Amplifier arrangement and method for operation of an amplifier arrangement

ABSTRACT

An amplifier arrangement is provided having a first differential amplifier stage and a second differential amplifier stage, which are connected to one another with negative feedback. The second differential amplifier stage has a first voltage divider that is connected to the controlled path of the second differential amplifier stage and has at least two signal taps. The second differential amplifier stage also has a second voltage divider with at least two signal taps. Furthermore, a switching device is provided, and is connected to the at least two signal taps of the first voltage divider and to the at least two signal taps of the second voltage divider. The switching device is used to connect one of the at least two signal taps of the first voltage divider to a first output tap of the amplifier arrangement, and one of the at least two signal taps of the second voltage divider to a second output tap of the amplifier arrangement. The overall input impedance can thus be adjusted in a suitable preferred manner.

REFERENCE TO RELATED APPLICATIONS

This application claims the benefit of the priority date of Germanapplication DE 10 2004 025 918.6, filed on May 27, 2004, the contents ofwhich are herein incorporated by reference in its entirety.

FIELD OF THE INVENTION

The present invention relates to an amplifier arrangement.

BACKGROUND OF THE INVENTION

In modern communication systems, signals which have been received via anantenna are first of all amplified by a particularly low-noise amplifier(LNA) to a suitable level. However, the input level of a signal that isreceived via the antenna is not known. The input amplifiers are thusvery frequently implemented with variable gain, in order in this way toamplify signals at different input levels to the same output level.

This is achieved, for example, via implementation of a low-noise inputamplifier with a stepped gain, which is also referred to as an amplifierwith a gain step. The use of an amplifier such as this simplifies thedesign of the downstream stages. However, one problem that has beenfound increasingly in this case is how to achieve a low capacitivecomponent of the input impedance with low-noise amplifiers implementedon the basis of CMOS technology. With fixed predetermined sourceimpedances such as those for GSM or WCDMA signals, the necessarymatching to 100 to 200 Ω can be achieved only with great difficulty.Owing to the increasing demand for bandwidth and high gain on the inputamplifiers, this matching problem is becoming even more serious.

Furthermore, modern mobile radio systems use an SAW filter in order tosuppress adjacent channel power in the received signal. However, thesefilters have the characteristic that they can convert differentiallysuppressed signals to DC signal components. Owing to the high power inthe adjacent channels, the additional signal components can lead to areduction in the sensitivity of the downstream stages. It is thusexpedient to provide a high level of Common mode rejection in additionin the input amplifier itself.

One possible way for doing this is transformation to a real inputimpedance by means of feedback with inductive components within theamplifier circuit. However, the formation of coils in this case in anintegrated circuit, particularly when based on silicon as thesemiconductor, occupies a very large area. This therefore also increasesthe production costs.

Another amplifier circuit which allows impedance transformation withoutany additional coils is shown in FIG. 3, which is known to theapplicant. In this case, the traditional concept of a differentialamplifier formed by the two field-effect transistors M1 and M2 isfollowed by a source follower formed from the two transistors M3 and M4.Input impedance transformation is achieved via the additional impedancesZ_(r), which connect the output of the amplifier circuit O and O_(x) tothe inputs In and Inx. With careful design, this amplifier circuitallows amplification with very low noise as well as suitable impedancetransformation, taking into account the output resistances of the twosource followers M3 and M4.

However, the source followers M3 and M4 considerably increase the powerconsumption. In addition, this circuit concept does not allow anyadditional gain and does not allow a stepped gain by means of a gainstep to be provided in a simple and efficient manner, in which the loopgain and thus the input impedance as well remain constant.

SUMMARY OF THE INVENTION

The following presents a simplified summary in order to provide a basicunderstanding of one or more aspects of the invention. This summary isnot an extensive overview of the invention, and is neither intended toidentify key or critical elements of the invention, nor to delineate thescope thereof. Rather, the primary purpose of the summary is to presentone or more concepts of the invention in a simplified form as a preludeto the more detailed description that is presented later.

The invention is directed to an amplifier circuit that provides highgain with an adjustable gain factor.

In one embodiment of the amplifier circuit, a first differentialamplifier stage and a second amplifier stage are provided. The first andthe second amplifier stages respectively contain a first and a secondcontrolled path, as well as a first and a second output node. The secondamplifier stage is in this case connected to the first differentialamplifier stage via negative feedback. In consequence, the secondamplifier stage is connected to the first differential amplifier stagein such a way that it forms a differential amplifier stage with negativefeedback. Furthermore, the second amplifier stage contains a first and asecond voltage divider, which are each connected in the differentialamplifier path and are connected to one of the two controlled paths. Thefirst and the second voltage divider in this case each have at least twosignal taps. Finally, a switching device is provided, by means of whicha first and a second output tap of the amplifier arrangement can beconnected to one of the at least two signal taps of the first and of thesecond voltage divider.

With the above configuration, the negative feedback achieves the maximumpossible gain and, in addition, a considerable improvement in the commonmode rejection. The connection of the voltage dividers to the signaltaps within the second differential amplifier stage results in the loopgain of the amplifier circuit according to the invention being keptconstant. The second amplifier stage is, in one example, a differentialamplifier stage.

The switching device, which connects a signal tap of the first and ofthe second voltage divider to the output tap of the amplifierarrangement according to the invention as a function of the respectiveswitch position, results in a gain step which depends on the voltageratios of the voltage divider. Suitable negative feedback allows thegain in the loop to remain constant irrespective of the switch position.

In one embodiment, the first and the second voltage divider each have atleast two series-connected resistors, with one of the at least twosignal taps of the first and of the second voltage divider beingarranged between the at least two series-connected resistors in thefirst and the second voltage divider. The first of the at least twosignal taps is, in one example, arranged between the voltage divider andthe controlled path of the differential amplifier. The gain step whichis provided by this embodiment results from the ratio of the firstresistance in the voltage divider to the sum of the two resistances. Ina further embodiment, the voltage divider is formed by current mirrorsrather than resistors.

In another embodiment of the invention, negative feedback is provided bya connection of the control input of the first controlled path of thesecond amplifier stage to the output tap of the second controlled pathof the first differential amplifier stage. The output tap of the firstcontrolled path of the first differential amplifier stage is connectedto the control input of the second controlled path of the secondamplifier stage.

In a further embodiment, the control connection of the first controlledpath is connected by a first connection of the first controlled path ofthe second differential amplifier stage, and the control connection ofthe second controlled path is connected to a first connection of thesecond controlled path of the second differential amplifier stage.

In still another embodiment, in order to obtain a positive influence onthe overall input impedance and to improve the linearity, in each caseone impedance and preferably one capacitance is connected between theconnection of the first and of the second controlled path of the firstdifferential amplifier stage and the control connection of the first andthe second controlled path of the second amplifier stage.

In a further embodiment, a matching of the input impedance of theamplifier arrangement according to the invention is improved byconnecting an impedance between the control connections of the first andof the second controlled path of the first differential amplifier stageand the respective first connections of the first and the secondcontrolled path of the second amplifier stage.

The impedance is used for impedance transformation of the outputimpedance to the input impedance. The resultant overall input impedanceis then a function of the input impedance of the first stage, theimpedance between the control connections, the output impedance of thesecond amplifier stage and, if appropriate, the input impedance of anydownstream circuit. In addition to a pure series capacitance, anadditional series or parallel resistive component may also be provided.This considerably improves the real part of the overall input impedance.

In a further embodiment, the switching device is designed usingfield-effect transistors, for example, using field-effect transistors ofa p-channel type. The first and the second controlled path in oneembodiment are each formed by at least one bipolar transistor. Thisadvantageously makes it possible to use the gradient of a bipolartransistor to save area and power in comparison to the previous coilsolutions.

To the accomplishment of the foregoing and related ends, the inventioncomprises the features hereinafter fully described and particularlypointed out in the claims. The following description and the annexeddrawings set forth in detail certain illustrative aspects andimplementations of the invention. These are indicative, however, of buta few of the various ways in which the principles of the invention maybe employed. Other objects, advantages and novel features of theinvention will become apparent from the following detailed descriptionof the invention when considered in conjunction with the drawings.

BRIEF DESCRIPTION OF THE DRAWINGS

The invention will be explained in detail in the following text usingexemplary embodiments and with reference to the drawings, in which:

FIG. 1 is a schematic diagram illustrating a first exemplary embodimentof the invention;

FIG. 2 is a schematic diagram illustrating a second exemplary embodimentof the invention; and

FIG. 3 is a schematic diagram illustrating a conventional amplifierarrangement.

DETAILED DESCRIPTION OF THE INVENTION

One embodiment of the amplifier arrangement according to the inventionas shown in FIG. 1 is in the form of an integrated circuit in asemiconductor body. Depending on the requirements, the integratedcircuit is formed using silicon technology, for example bipolarcomplementary metal oxide semiconductor technology, which is abbreviatedto Bi-CMOS or GaAs technology. However, other semiconductor systems ortechnologies may also be used. A number of connecting contacts areprovided on the surface of the semiconductor body and are used to carrysignals, but are also used to supply the integrated circuit. In additionto the amplifier arrangement according to the invention, thesemiconductor body may contain additional integrated circuits forfurther signal processing.

The amplifier arrangement according to the invention has a firstdifferential amplifier 1 as well as a second differential amplifier 2with feedback. The first differential amplifier has a first controlledpath M1 and a second controlled path M2, which are each formed byfield-effect transistors. The source connections of the two field-effecttransistors M1 and M2 are connected to a current source Q2. The drainconnections are each passed via two load resistors R₁ and R₂ to thesupply potential connection VC. The gain is dependent on the loadresistances R₁ and R₂. It can thus be defined as the product of thetransconductance gm of the transistors M₁ and M₂ and of the loadresistances R₁ and R₂. The control inputs of the two field-effecttransistors M1 and M2 form the signal input of the amplifier arrangementaccording to the invention.

The second differential amplifier stage 2 likewise contains twofield-effect transistors M3 and M4, whose source connections areconnected to a second current source Q1. In this exemplary embodiment,the current sources Q1 and Q2 are formed by two different, separatecurrent sources. However, it is also possible to use a common currentsource. The drain connection of the transistor M3 is connected to afirst resistor R₃₁, which is followed by a second resistor R₃₂. The tworesistors R₃₁ and R₃₂ form a first voltage divider with the two taps A3and A5, respectively. The drain connection of the transistor M4 isconnected in the same way to the resistor R₄₁ and to the resistor R₄₂that is connected in series with it. These two resistors also form avoltage divider with the two taps A4 and A6, respectively. Furthermore,the respective second connections of the voltage dividers or of theresistors R₃₂ and R₄₂ are connected to the supply potential connectionVC.

In order to provide negative feedback for the two differential amplifierstages 1 and 2, a first output node A1 between the first transistor M1and the first load resistance R₁ is connected to the control connectionof the second transistor M4 in the second differential amplifier stage2. At the same time, a second output node A2 between the second loadresistance R₂ and the second transistor M2 in the first differentialamplifier stage 1 is connected to the control connection of thefield-effect transistor M3 in the second differential amplifier 2. Atthe same time, the control connection of the first field-effecttransistor M1 in the first differential amplifier stage 1 is connectedvia a complex impedance Z₂ to the drain connection of the firsttransistor M3 in the second differential amplifier 2.

The drain connection of the second field-effect transistor M4 in thesecond differential amplifier stage 2 is coupled via a further impedanceZ₁ to the control connection of the second field-effect transistor M2.These connections between the output nodes A1 and A2 of the firstdifferential amplifier stage 1 and the control connections of the twofield-effect transistors M3 and M4 in the second differential amplifierstage 2, as well as the drain connections of the two field-effecttransistors M₃, M₄ in the second differential amplifier stage and thecontrol connections of the field-effect transistors M₁, M₂ in the firstdifferential amplifier stage 1 provide negative feedback for the twodifferential amplifiers 1 and 2. In an alternative embodiment, theseconnections may be provided by couplings, and may have impedances.

The two impedances Z1 and Z2 are also referred to as feedback impedancesand have a positive influence on the overall input impedance of thecircuit. If suitably designed, the real part of the overall inputimpedance is increased, and the imaginary component is reduced. Inconjunction with the output impedance and the input impedance of thefirst stage 1, the two impedances Z₁ and Z₂ thus transform the overallinput impedance. They are expediently designed to be controllable, forexample by means of variable resistances and/or controllablecapacitances. One example of this is varactor diodes. In this case, itis also possible to provide impedance networks composed of paralleland/or series-connected capacitances and/or resistances.

This impedance results in the maximum possible gain for the two stagesand, at the same time, in greater common mode signal rejection than inthe conventional circuit shown in FIG. 3. The common mode signalcomponent in the two output nodes A1 and A2 of the first amplifier stage1 is used to set the operating point of the two field-effect transistorsM3 and M4 in the second differential amplifier stage 2.

Furthermore, the amplifier arrangement according to the inventioncontains a switching device S, which contains four switches S₁₁, S₁₂,S₂₁ and S₂₂. In this case, the output tap A3 is coupled via the switchS₂₂ and the output tap A5 is coupled via the switch S₁₁ to the outputtap O_(X) of the amplifier arrangement according to the invention. Theoutput tap O for the difference signal is connected via switches S₂₁ tothe output tap A4, and via the switch S₁₂ to the output tap A6 of thesecond voltage divider. These switches result in a gain step in theamplification. At the same time, the loop gain within the feedbackamplifier circuits is also kept constant. In consequence, the influenceof the output impedance and the input impedance of the amplifierarrangement is largely independent of the switch position.

If, for example, the two switches S₁₁ and S₁₂ are closed, then, to afirst approximation, the gain V₁, V₂ in the two differential amplifierpaths can be described by the following equations:V ₁ =g _(M1) *g _(M3) *R ₁ *Z ₂*(R ₃₁ +R ₃₂)/(R ₃₁ +R ₃₂ +Z ₂)V ₂ =g _(M2) *g _(M4) *R ₂ *Z ₁*(R ₄₁ +R ₄₂)/(R ₄₁ +R ₄₂ +Z ₁)

In the opposite switch position, that is to say when the switches S₁₁and S₁₂ are open, the amplification of the voltage drop, which is nowreduced, is reduced to the gainV ₁ =g _(M1) *g _(M3) *R ₁ *R ₃₂ *Z ₂/(R ₃₁ +R ₃₂ +Z ₂)V ₂ =g _(M2) *g _(M4) *R ₂ *R ₄₂ *Z ₁/(R ₄₁ +R ₄₂ +Z ₁)

Thus, depending on the switch position this results in a stepped gainsetting by a factor R₃₂/(R₃₁+R₃₂). Since the connections for thefeedback are connected between the voltage divider formed by therespective resistors R₃₁, R₃₂ and R₄₁, R₄₂ and the drain connections ofthe field-effect transistors M₃ and M₄, the gain within the loop remainsconstant irrespective of the selected switch position.

Finally, impedances with controllable capacitances in the form ofcapacitors C₁ and C₂ are connected between the drain connection of thetransistor M3 and the control connection of the transistor M3, as wellas between the drain connection of the transistor M4 and the controlconnection of the transistor M4. The capacitors C₁ and C₂ allow thegate/drain capacitances of the field-effect transistors M1 to M4 to bevaried in order in this way to optimize the influence of the outputimpedance of the second amplifier stage 2 on the transformation result.Further impedances Z3, Z4 and Z7, Z8 are connected between the controlconnections and source connections of the field-effect transistors M3,M4 and M1, M2. Together with the two impedances Z1, Z2, the impedancesZ3 and Z4 improve the linearity of the second differential amplifierstage 2, improving the transformation result, and hence the overallinput impedance. The linearity of the first differential amplifier stage1 is optimized by means of the impedances Z5 to Z8, which are likewisein the form of capacitors.

FIG. 2 shows a further refinement of the invention. Components whichhave the same function as that in FIG. 1 are annotated with the samereference symbols. The first differential amplifier stage 1 is in thiscase formed by two parallel-connected bipolar transistors M5 and M6,rather than by field-effect transistors. Since a bipolar transistor hasa steeper gradient than a field-effect transistor, this allows thesurface area and the power consumption to be reduced. The collectorconnections of the two bipolar transistors M5 and M6 are each connectedto a field-effect transistor in a current mirror CS.

The current mirror CS is formed together with a current mirrortransistor CS1, whose control connection is connected to its sourceconnection and to the respective control connection of, in each case,one field-effect transistor in the current mirror CS in the firstdifferential amplifier stage 1. The current flow through the twofield-effect transistors in the current mirror CS, and thus theresistance of the two field-effect transistors, is formed by a currentsource CR which is connected to the source connection of the currentmirror transistor CS1.

Furthermore, the switches S₁₁, S₁₂, S₂₁ and S₂₂ are in the form of PMOSfield-effect transistors. The control connections of the two transistorsS₂₁ and S₁₂ as well as S₁₁ and S₂₂ are connected to a bus SA forsupplying a control signal. The bus SA is formed by a number of signallines. A normal control connection can also be provided, and is coupledto all of the switches. In this case, two associated switches must beconnected to the connection SA via an inverter.

Since the internal resistance of the transistors when they are switchedon is reflected directly in the noise factor, it is expedient to designthem to have as low a resistance as possible, and thus also to have aslarge a surface area as possible. However, this also results inparasitic capacitances being increased. The switches thus have aslightly low-pass filter characteristic, which has a negative influencenot only on the gain/bandwidth product, but also on the gain step. Thefield-effect transistors reduce the dominant pole, so that the absolutegain and the bandwidth are reduced. They must be appropriatelydimensioned.

Furthermore, the resistors R₃₂ and R₄₂ in the first and second voltagedividers are in the form of resistances which can be adjusted by meansof a control signal via the bus SA. This makes it possible to adjust thegain factor and thus the gain step of the amplifier arrangementaccording to the invention.

Furthermore, the respective impedances Z₁ and Z₂ are in the form ofrespective capacitors CZ1 and CZ2, and thus series-connected resistorsRZ1 and RZ2. This series capacitance with the upstream resistanceincreases the real component for the matching of the input impedance ofthe amplifier arrangement according to the invention. However, theintroduction of the resistors RZ1 and RZ2 in the negative feedback pathmakes the noise factor worse. As good a compromise as possible musttherefore be found, in some suitable manner.

The two concepts proposed here may be combined with one another in anydesired manner. Other embodiments, for example using BiCMOS or a purebipolar technology, can also be implemented. The circuit or individualelements can also be implemented using a different conductance type tothat described here. Furthermore, it is possible not only to connect thetwo differential amplifiers described here to one another with negativefeedback, but also to provide further differential amplifier stages inorder to achieve even more gain in this way.

The inclusion of the switchable load resistances in the finaldifferential amplifier stage means that the loop gain within thearrangement is independent of the switch position. The common modesignal component in each stage is in this case used to set the operatingpoint of the respective subsequent stage. This also results inconstraints for the two load resistances R1 and R2 and for the currentmirror CS (which is illustrated in FIG. 2) in the first differentialamplifier stage 1.

A further embodiment is formed by AC coupling at the control inputs ofthe field-effect transistors M3 and M4 in the second differentialamplifier stage 2. This could be done, for example, by provision of aseries-connected capacitor between the two output taps A1 and A2 of thefirst stage and the control connections of the transistors M3 and M4. Anadditional, separate bias circuit is then required in order to set theoperating points of the field-effect transistors M3 and M4 in the secondstage 2. The amplifier arrangement may be used not only for receivers,but also for transmitters. Furthermore, the two described embodimentscan be combined in any desired manner, and can also be extended, forexample by further amplifier stages.

While the invention has been illustrated and described with respect toone or more implementations, alterations and/or modifications may bemade to the illustrated examples without departing from the spirit andscope of the appended claims. In particular regard to the variousfunctions performed by the above described components or structures(assemblies, devices, circuits, systems, etc.), the terms (including areference to a “means”) used to describe such components are intended tocorrespond, unless otherwise indicated, to any component or structurewhich performs the specified function of the described component (e.g.,that is functionally equivalent), even though not structurallyequivalent to the disclosed structure which performs the function in theherein illustrated exemplary implementations of the invention. Inaddition, while a particular feature of the invention may have beendisclosed with respect to only one of several implementations, suchfeature may be combined with one or more other features of the otherimplementations as may be desired and advantageous for any given orparticular application. Furthermore, to the extent that the terms“including”, “includes”, “having”, “has”, “with”, or variants thereofare used in either the detailed description and the claims, such termsare intended to be inclusive in a manner similar to the term“comprising”.

List of reference symbols 1, 2: Differential amplifier stage M1, M2, M3,M4: Field-effect transistors M5, M6: Bipolar transistors Q1, Q2: Currentsources VC: Supply potential connection R1, R2: Load resistors R31, R41,R32, R42: Voltage divider resistors A1, A2: Output nodes A3, A4, A5, A6:Signal tap In, Inx: Signal input O, O_(x): Signal output Z1, Z2: Compleximpedance Z3, Z4, Z5: Impedance Z6, Z7, Z8: Impedance CS: Current mirrorCS1: Current mirror transistor CR: Current source C1, C2, CZ1, CZ2:Capacitors S: Switching device S11, S12, S22, S21: Switches SA: Buscontrol signal connection VC: Supply potential connection

1. An amplifier arrangement, comprising: a first output tap and a secondoutput tap forming a differential output of the amplifier arrangement; afirst differential amplifier stage comprising a first controlled pathand a first output node, and comprising a second controlled path and asecond output node; a second differential amplifier stage comprising athird controlled path and a fourth controlled path, and coupled to thefirst and second controlled paths of the first differential amplifierstage and to the first and second output nodes of the first differentialamplifier stage such that the coupling forms a negative feedbackarrangement, the second differential amplifier stage further comprisinga first voltage divider connected to the third controlled path andcomprising at least two signal taps, and a second voltage dividerconnected to the fourth controlled path and comprising at least twosignal taps; and a switching device connected to the at least two signaltaps of the first voltage divider and to the at least two signal taps ofthe second voltage divider, and configured to selectively connect one ofthe at least two signal taps of the first voltage divider to the firstoutput tap, and one of the at least two signal taps of the secondvoltage divider to the second output tap.
 2. The amplifier arrangementof claim 1, wherein a first of the at least two signal taps of the firstvoltage divider is arranged between the first voltage divider and thethird controlled path, and a first of the at least two signal taps ofthe second voltage divider is arranged between the second voltagedivider and the fourth controlled path.
 3. The amplifier arrangement ofclaim 2, wherein the first voltage divider and the second voltagedivider each comprise at least two series-connected resistors, with asecond of the at least two signal taps of the first voltage divider andthe second voltage divider are arranged between the at least twoseries-connected resistors, respectively.
 4. The amplifier arrangementof claim 1, wherein the switching device comprises one or morefield-effect transistors.
 5. The amplifier arrangement of claim 1,wherein the first controlled path and the second controlled path of thefirst differential amplifier stage each have a control connection thatcollectively form a differential signal input of the amplifierarrangement, and wherein a respective first connection of the firstcontrolled path and the second controlled path is coupled to a supplypotential.
 6. The amplifier arrangement of claim 5, wherein the firstconnections of the first and second controlled paths are connected via acurrent mirror to the supply potential.
 7. The amplifier arrangement ofclaim 1, wherein the first output node of the first differentialamplifier stage is connected to a control connection of the fourthcontrolled path and, via a first charge store, to a first connection ofthe fourth controlled path, and wherein the second output node of thefirst differential amplifier stage is connected to a control connectionof the third controlled path and, via a second charge store, to a firstconnection of the third controlled path.
 8. The amplifier arrangement ofclaim 7, wherein a control connection of the first controlled path iscoupled to the first connection of the third controlled path, and acontrol connection of the second controlled path is connected to thefirst connection of the fourth controlled path.
 9. The amplifierarrangement of claim 1, wherein the first and the second controlledpaths each comprise at least one field-effect transistor.
 10. Theamplifier arrangement of claim 1, wherein the first and the secondcontrolled paths each comprise at least one bipolar transistor.
 11. Theamplifier arrangement of claim 1, further comprising means fortransforming a real part and an imaginary part of the overall inputimpedance of the amplifier arrangement provided between the firstdifferential amplifier stage and the second differential amplifierstage.
 12. An amplifier arrangement, comprising: a first output tap anda second output tap forming a differential output of the amplifierarrangement; a first differential amplifier stage comprising a firstcontrolled path and a first output node, and comprising a secondcontrolled path and a second output node; a second differentialamplifier stage comprising a third controlled path and a first voltagedivider connected to the third controlled path, the first voltagedivider comprising at least two signal taps, the second differentialamplifier stage further comprising a fourth controlled path and a secondvoltage divider connected to the fourth controlled path, the secondvoltage divider comprising at least two signal taps, wherein the firstoutput node of the first differential amplifier stage is coupled to acontrol connection of the fourth controlled path, wherein the secondoutput node of the first differential amplifier stage is coupled to acontrol connection of the third controlled path, wherein one of the atleast two signal taps of the first voltage divider is arranged betweenthe third controlled path and the first voltage divider, and is coupledto a control connection of the first controlled path, and wherein one ofthe at least two signal taps of the second voltage divider is arrangedbetween the fourth controlled path and the second voltage divider, andis coupled to a control connection of the second controlled path. 13.The amplifier arrangement of claim 12, further comprising a switchingdevice connected to the at least two signal taps of the first voltagedivider and to the at least two signal taps of the second voltagedivider, and configured to selectively connect one of the at least twosignal taps of the first voltage divider to the first output tap, andone of the at least two signal taps of the second voltage divider to thesecond output tap.
 14. The amplifier arrangement of claim 12, whereinthe first voltage divider and the second voltage divider each compriseat least two series-connected resistors, wherein a second of the atleast two signal taps of the first and of the second voltage dividersare arranged between the at least two series-connected resistors in thefirst and the second voltage dividers, respectively.
 15. The amplifierarrangement of claim 12, wherein the first controlled path and thesecond controlled path of the first differential amplifier stage eachcomprise a control connection that collectively form a differentialsignal input of the amplifier arrangement, and a respective firstconnection of the first and of the second controlled path is coupled toa supply potential.
 16. An amplifier arrangement, comprising: a firstoutput tap and a second output tap forming a differential output of theamplifier arrangement; a first differential amplifier stage comprising afirst controlled path and a first output node, and comprising a secondcontrolled path and a second output node; a second differentialamplifier stage comprising a third controlled path and a fourthcontrolled path, which are coupled to respective ones of the first andsecond controlled paths of the first differential amplifier stage and tothe first and second output nodes of the first differential amplifierstage such that the second differential amplifier stage provides anegative feedback to the first differential amplifier stage, the seconddifferential amplifier stage further comprising a first voltage dividerconnected to the third controlled path and comprising at least twosignal taps, and comprising a second voltage divider connected to thefourth controlled path and comprising at least two signal taps; a firstfield-effect transistor configured to selectively couple a first of theat least two signal taps of the first voltage divider that is connectedbetween the third controlled path and the first voltage divider to thefirst output tap; at least one second field-effect transistor configuredto selectively couple a second of the at least two signal taps of thefirst voltage divider that is connected between at least twoseries-connected resistors in the first voltage divider to the firstoutput tap; a third field-effect transistor configured to selectivelycouple a first of the at least two signals taps of the second voltagedivider that is connected between the fourth controlled path and thesecond voltage divider to the second output tap; and at least one fourthfield-effect transistor configured to selectively couple a second of theat least two signal taps of the second voltage divider that is connectedbetween at least two series-connected resistors in the second voltagedivider to the second output tap, wherein either the first or secondfield-effect transistor are switched on at a given time, and either thethird or fourth field-effect transistor are switched on at the giventime.
 17. The amplifier arrangement of claim 16, wherein the secondfield-effect transistor comprises a complementary field-effecttransistor to the first field-effect transistor, and the fourthfield-effect transistor comprises a complementary field-effecttransistor to the third field-effect transistor, and the first and thesecond field-effect transistors are connected at their respectivecontrol connections to a signal line of a bus, and the third and thefourth field-effect transistor are connected at their respective controlconnections to a further signal line of the bus.
 18. The amplifierarrangement of claim 16, wherein the first or the second, and the thirdor the fourth field-effect transistors comprise PMOS field-effecttransistors.